Amplifier power supply on ir2153. A simple switching power supply on ir2153 (d) for an amplifier and not only

The power supply is built on a floor-bridge circuit based on the IR2153 chip. At the output of this block, you can get any voltage you need, it all depends on the parameters of the secondary winding of the transformer.

Let's take a closer look at the diagram. impulse block nutrition.

The power of the power supply with just such components is about 150 watts.

Mains alternating voltage through a fuse and a thermistor is supplied to the diode rectifier.

After the rectifier, there is an electrolytic capacitor, which, at the moment the unit is connected to the network, will be charged with a large current, the thermistor just limits this current. A capacitor is needed with a voltage of 400-450 volts. Further constant pressure goes to the power keys. At the same time, power is supplied to the IR2153 chip through a limiting resistor and a rectifier diode.

You need a powerful resistor, at least 2 watts, it is better to take a 5-watt one. The supply voltage for the microcircuit is additionally smoothed out by a small electrolytic capacitor with a capacity of 100 to 470 microfarads, preferably 35 volts. The microcircuit begins to generate a sequence of rectangular pulses, the frequency of which depends on the value of the components of the timing circuit, in my case, the frequency is in the region of 45 kHz.

A rectifier with a midpoint is installed at the output. Rectifier in the form of a diode assembly in the TO-220 package. If the output voltage is planned within 40 volts, then diode assemblies soldered from computer power supplies can be used.

The voltage boost capacitor is designed for the correct operation of the upper field switch, the capacitance depends on which transistor is used, but on average 1 uF is enough for most cases.

Before starting, you need to check the operation of the generator. For these purposes, about 15 volts of direct voltage is supplied from an external power source to the indicated pins of the microcircuit.
Next, the presence of rectangular pulses on the gate of the field keys is checked, the pulses must be completely identical, of the same frequency and filling.
The first start-up of the power supply must be done through a 220-volt safety incandescent lamp with a power of about 40 watts, be extremely careful not to touch the board during operation, after disconnecting the unit from the mains, wait a few minutes until the high-voltage capacitor is discharged through the appropriate resistor.
It is very important to point out that this circuit does not have short circuit protection, therefore any short circuits, even short ones, will lead to the failure of the power switches and the IR2153 chip, so be careful.

Good afternoon! My opinion: The scheme (first) will work, everything you need is there! Tips to replace the driver, add capacity, etc. there are unfounded. If something is changed, then this is a separate scheme and other discussions. The weak point is capacitors with a midpoint of 200 V! Yes, it will work, but if the capacitor could, he expressed his wish to increase the breakdown voltage to 350 V! It's just a filter - half the trouble, but decoupling the load and working on the transformer winding is another. We consider, and who is not too lazy: 310 V (for example, power supply) + 150 V (EMF of the transformer inductance discharge) = 460 V. Half equals 230 volts. Or maybe "BOOM!" - maybe, but it will be "p-sh-sh-sh-i-k!" and the capacitor will leak. Like clearly explained. And the scheme will work and give what it was counted on! Fact! Protection! The most good protection- the one that is simple! Those. fuse both at the inlet and outlet. The fuse operation speed is sufficient for the key pulse current time of 25 A! Do you understand that this is enough? Enough. To obtain maximum efficiency, you need to select the pulse frequency for the transformer used, this is obvious. ferrite was heated to 100 gr. lost properties, the calculation will be adjusted. How to choose is easy. We measure the current consumption of the circuit after the rectifier. By changing the frequency from higher to lower, we find the moment of current increase - stop! We increase the frequency by 1-2 kHz. Everything! How to change the frequency? Simply, replace the resistor Rt with a trimmer of greater resistance (without fanaticism). You also need to select the frequency for the transformer from the computer's power supply. The spread of operating frequencies from 32 kHz to 55 kHz. Success to all. As for the second scheme, this is a variant of all the errors of the first and some other schemes from the Internet! Why? The first and most important in the "datasheet" IR2153 IRF740 are clear contradictions: the breakdown voltage is not less than 600 V. and the keys are 400v. The gate capacitance for 2153 (load) is no more than 1000 pF, and for 740 = 1400 pF. Yes, the bulbs will glow, but with this block you are doomed to purchase more than one set of parts. The output voltage will sag - there is no required pulse steepness. The efficiency will be below the maximum, we warm the environment. In general, the selection of parts of the (second) circuit is a mistake! The 740 requires a 2155 driver (manufacturer's recommendation) capacitance up to 2200 pf in load. The scheme is an experiment with an explosion! Collect strictly with glasses and gloves! What would I put together? Keys STP5NK60C (or 4NK60, 6NK60, 7NK60...)< 1000 пф. Остальное все рабочее, правда я бы подобрал частоту и ток драйвера как описал выше. Напомню: запас в электронике не всегда уместен. Скажем взять ключи на пробой в 1000 в - это неправильно. IRF740 - отличные ключи для применения в Китае, напряжение сети 110 - 120 в. Как то так.

Power supply IR2153 500W- I suggest that you familiarize yourself with, and if you wish, repeat the circuit of a switching power supply for a power amplifier implemented on the well-known IR2153. This is a self-clocked half-bridge driver, an improved modification of the IR2151 driver, which includes a high-voltage half-bridge program with a generator equivalent to the 555 integrated timer (K1006VI1). A distinctive feature of the IR2153 chip is the improved functionality and does not require special skills in its use, a very simple and effective device relative to early-produced microcircuits.

Distinctive properties of this power supply:

• A protection circuit against possible overloads is implemented, as well as protection in case of a short circuit in the windings of a pulse transformer.
• Built-in power supply soft start circuit.
• It has the function of protecting the device at the input, which is performed by a varistor that protects the PSU from voltage surges in the mains and its excessive value, as well as from accidental supply of 380v to the input.
• Easy to learn and inexpensive scheme.

The characteristics that it has power supply IR2153 500W
The rated output power is 200W, if you use a transformer with a higher power, you can get 500W.
Musical or RMS output power is 300W. You can get 700W with a higher power transformer.
Operating frequency standard - 50kHz
The output voltage is - two shoulders of 35v. Depending on what voltage the transformer is wound on, it is possible to take the corresponding output voltage values.
Coefficient useful action is 92%, but also depends on the design of the transformer.

The power supply control circuit is standard for the IR2153 chip and is borrowed from its datasheet. The short circuit and overload protection module has the ability to set the current at which cutoff will occur with the simultaneous activation of the signal LED. When the power supply switches to protection mode in case of an emergency, it can stay in this state for an unlimited time, although the device's current consumption will remain comparable to the idle current of an unloaded PSU. As for the sample of my modification, there the protection is set to limit the power consumption of the power supply from 300 W, which guarantees against excessive load, and therefore from excessive heating, which in turn is fraught with the failure of the entire unit.

Load testing moment

Here is the file, everything regarding the power supply is described in detail, and there are also recommendations on how to increase the output power. Any radio amateur, having read this material, is able to independently manufacture a power supply for the power he needs and, accordingly, the output voltage.

A compressed folder with a transformer calculation method and a program attached to it.
Download:
Download:

A program for calculating the nominal values ​​of components for assigning the required frequency of operation of the IR2153.
Download:

Printed circuit board.
Download:

The printed circuit board is designed to install a computer transformer and output ultra-fast diodes such as MUR820 and BYW29-200, thereby making it possible to use it in power supplies with a power of 250 W at the output. But there is also a weak spot - this is a platform for capacitor C3. If there is no capacitor suitable for the diameter, then the board will need to be slightly moved apart.
For PCB LUT mirror image do not need to.

An informative article on using IR drivers.
Download:

Here is a slightly modified power supply. Its fundamental difference from the above scheme is in the implemented protection device.

So the first power supply, let's conditionally call it "high-voltage":

The circuit is classic for my switching power supplies. The driver is powered directly from the mains through a resistor, which reduces the power dissipated on this resistor, compared to powering from the +310V bus. This power supply has a soft start (inrush current limit) circuit on the relay. Soft start is powered by a quenching capacitor C2 from a 230V network. This power supply is equipped with protection against short circuit and overload in the secondary circuits. The current sensor in it is the resistor R11, and the current at which the protection is triggered is regulated by the tuning resistor R10. When the protection is triggered, the HL1 LED lights up. This power supply can provide output bipolar voltage up to +/-70V (with these diodes in the secondary circuit of the power supply). The pulse transformer of the power supply has one primary winding of 50 turns and four identical secondary windings of 23 turns. The cross section of the wire and the core of the transformer are selected based on the required power that must be obtained from a particular power supply.

The second power supply, we will conditionally call it a “self-powered UPS”:

This unit has a circuit similar to the previous power supply, but the fundamental difference from the previous power supply is that in this circuit, the driver feeds itself from a separate transformer winding through a quenching resistor. The remaining nodes of the scheme are identical to the previous presented scheme. output power and the output voltage of this unit is limited not only by the parameters of the transformer, and the capabilities of the IR2153 driver, but also by the capabilities of the diodes used in the secondary circuit of the power supply. In my case, this is KD213A. With these diodes, the output voltage cannot be more than 90V, and the output current cannot be more than 2-3A. The output current can be higher only if radiators are used to cool the KD213A diodes. It is worthwhile to additionally dwell on the T2 throttle. This inductor is wound on a common ring core (other types of cores can also be used), with a wire of the section corresponding to the output current. The transformer, as in the previous case, is calculated for the corresponding power using specialized computer programs.

Power supply number three, let's call it "powerful on 460x transistors" or simply "powerful 460":

This scheme is already more significantly different from the previous schemes presented above. There are two main big differences: protection against short circuit and overload is performed here on a current transformer, the second difference is the presence of additional two transistors in front of the keys, which allow isolating the high input capacitance of powerful keys (IRFP460) from the driver output. Another small and not significant difference is that the limiting resistor of the soft start circuit is located not in the +310V bus, as it was in the previous circuits, but in the 230V primary circuit. The circuit also contains a snubber connected in parallel with the primary winding of the pulse transformer to improve the quality of the power supply. As in the previous schemes, the protection sensitivity is regulated by a trimmer resistor (in this case, R12), and the HL1 LED signals the protection operation. The current transformer is wound on any small core that you have at hand, the secondary windings are wound with a wire of small diameter 0.2-0.3 mm, two windings of 50 turns each, and the primary winding is one turn of wire sufficient for your output power section.

And the last impulse for today is a “switching power supply for light bulbs”, we will conditionally call it that.

Yes, don't be surprised. Once there was a need to assemble a guitar preamplifier, but the necessary transformer was not at hand, and then this pulser, which was built just for that occasion, helped me a lot. The scheme differs from the previous three in its maximum simplicity. The circuit does not have, as such, protection against a short circuit in the load, but there is no need for such protection in this case, since the output current through the secondary bus + 260V is limited by resistor R6, and the output current through the secondary bus + 5V is limited by the internal overload protection circuit of the stabilizer 7805. R1 limits the maximum inrush current and helps cut off mains noise.

PULSE POWER SUPPLY WITH YOUR HANDS ON IR2153

Functionally, the IR2153 microcircuits differ only in the diode installed in the planar package.

Functional diagram IR2153

Functional diagram of IR2153D

To begin with, let's look at how the microcircuit itself works, and only then we will decide which power supply to assemble from it. First, let's look at how the generator itself works. The figure below shows a fragment of a resistive divider, three op-amps and an RS flip-flop:

At the initial moment of time, when the supply voltage was just applied, the capacitor C1 is not charged at all the inverting inputs of the op-amp, there is zero, and at the non-inverting positive voltage generated by the resistive divider. As a result, it turns out that the voltage at the inverting inputs is less than at the non-inverting ones, and all three op-amps at their outputs form a voltage close to the supply voltage, i.e. log unit.
Since the input R (setting zero) on the trigger is inverting, then for it it will be a state in which it does not affect the state of the trigger, but at the input S there will be a one log, which also sets a log one at the trigger output and the capacitor Ct through the resistor R1 will start charging. On the image voltage across Ct shown as blue line,red - voltage at the output DA1, green - at the output DA2, a pink - at the RS trigger output:

As soon as the voltage at Ct exceeds 5 V, a log zero is formed at the output of DA2, and when, while continuing to charge Ct, the voltage reaches a value slightly more than 10 volts, a log zero will appear at the output of DA1, which in turn will set the RS trigger to a log zero state. From this moment, Ct will begin to discharge, also through the resistor R1, and as soon as the voltage across it becomes slightly less than the set value of 10 V, a log unit will again appear at the DA1 output. When the voltage on the capacitor Ct becomes less than 5 V, a log unit will appear at the output of DA2 and turn the RS flip-flop into a one state and Ct will start charging again. Of course, at the inverted output RS of the flip-flop, the voltage will have opposite logical values.
Thus, at the outputs of the RS trigger, opposite in phase, but equal in duration, log one and zero levels are formed:

Since the duration of the control pulses IR2153 depends on the charge-discharge rate of the capacitor Ct, it is necessary to carefully pay attention to flushing the board from the flux - there should not be any leaks from either the capacitor terminals or the printed circuit conductors of the board, since this is fraught with magnetization of the power transformer core and failure power transistors.
There are also two more modules in the microcircuit - UV DETECT and LOGIK. The first of them is responsible for the start-stop of the generator process, depending on the supply voltage, and the second generates pulses DEAD TIME, which are necessary to exclude the through current of the power stage.
Then there is a separation of logical levels - one becomes the control upper arm of the half-bridge, and the second the lower one. The difference lies in the fact that the upper arm is controlled by two field-effect transistors, which, in turn, control the final stage "torn off" from the ground and "torn off" from the supply voltage. Considering the simplified circuit diagram turning on IR2153, it turns out something like this:

Pins 8, 7, and 6 of the IR2153 are the VB, HO, and VS outputs, respectively, i.e. high-side control power supply, the output of the high-side control final stage, and the negative wire of the high-side control module. Attention should be paid to the fact that at the moment of switching on, the control voltage is present at the Q RS of the flip-flop, therefore the low-side power transistor is open. Through the diode VD1, the capacitor C3 is charged, since its lower output is connected to a common wire through the transistor VT2.
As soon as the RS trigger of the microcircuit changes its state, VT2 closes, and the control voltage at pin 7 of the IR2153 opens the transistor VT1. At this point, the voltage at pin 6 of the microcircuit begins to increase, and to keep VT1 open, the voltage at its gate must be greater than at the source. Since the resistance of an open transistor is equal to tenths of an ohm, the voltage at its drain is not much greater than at the source. It turns out that keeping the transistor in the open state requires a voltage of at least 5 volts more than the supply voltage, and it really is - the capacitor C3 is charged up to 15 volts and it is he who allows you to keep VT1 in the open state, since the energy stored in it in this the moment of time is the supply voltage for the upper arm of the window stage of the microcircuit. Diode VD1 at this point in time does not allow C3 to be discharged to the power bus of the microcircuit itself.
As soon as the control pulse at pin 7 ends, the transistor VT1 closes and then VT2 opens, which again recharges the capacitor C3 to a voltage of 15 V.

Quite often, in parallel with capacitor C3, amateurs install an electrolytic capacitor with a capacity of 10 to 100 microfarads, without even delving into the need for this capacitor. The fact is that the microcircuit is capable of operating at frequencies from 10 Hz to 300 kHz and the need for this electrolyte is relevant only up to frequencies of 10 kHz, and then, provided that the electrolytic capacitor is of the WL or WZ series, they technologically have a small ers and are better known as computer capacitors with inscriptions in gold or silver paint:

For popular conversion frequencies used in the creation of switching power supplies, frequencies are taken above 40 kHz, and sometimes adjusted to 60-80 kHz, so the relevance of using an electrolyte simply disappears - even a capacitance of 0.22 uF is already enough to open and hold the SPW47N60C3 transistor in the open state , which has a gate capacitance of 6800 pF. To calm my conscience, a 1 uF capacitor is placed, and giving an amendment to the fact that IR2153 cannot switch such powerful transistors directly, then the accumulated energy of capacitor C3 is enough to control transistors with a gate capacitance of up to 2000 pF, i.e. all transistors with a maximum current of about 10 A (the list of transistors is below in the table). If you still have doubts, then instead of the recommended 1 uF, use a 4.7 uF ceramic capacitor, but this is pointless:

It would not be fair not to note that the IR2153 chip has analogues, i.e. microchips with similar functionality. These are IR2151 and IR2155. For clarity, we will summarize the main parameters in a table, and only then we will figure out which of them is better to cook:

CHIP	Max Voltage drivers	Start supply voltage	Stop supply voltage	Maximum current for driving the gates of power transistors / rise time	Maximum current for discharging the gates of power transistors / fall time	Internal zener voltage
				100 mA / 80...120 nS	210 mA / 40...70 nS
				NOT SPECIFIED / 80...150 nS	NOT SPECIFIED / 45...100 nS
				210 mA / 80...120 nS	420 mA / 40...70 nS

As can be seen from the table, the differences between the microcircuits are not very large - all three have the same shunt zener diode for power supply, the start and stop supply voltages for all three are almost the same. The difference lies only in the maximum current of the final stage, which determines which power transistors and at what frequencies the microcircuits can control. Strange as it may seem, but the most hyped IR2153 turned out to be neither fish nor meat - it does not have a normalized maximum current of the last driver stage, and the rise-fall time is somewhat prolonged. They also differ in cost - IR2153 is the cheapest, but IR2155 is the most expensive.
The generator frequency, it is the conversion frequency ( no need to divide by 2) for IR2151 and IR2155 is determined by the formulas below, and the frequency of IR2153 can be determined from the graph:

In order to find out which transistors can be controlled by the IR2151, IR2153 and IR2155 microcircuits, you should know the parameters of these transistors. Of greatest interest when docking a microcircuit and power transistors is the gate energy Qg, since it is it that will affect the instantaneous values ​​​​of the maximum current of the microcircuit drivers, which means that a table with transistor parameters is required. Here SPECIAL attention should be paid to the manufacturer, since this parameter has different manufacturers is different. This is most clearly seen in the example of the IRFP450 transistor.
I understand perfectly well that for a one-time production of a power supply unit, ten to twenty transistors are still a bit too much, nevertheless, I posted a link for each type of transistor - I usually buy there. So click, see prices, compare with retail and the likelihood of buying a leftist. Of course, I do not claim that Ali has only honest sellers and all goods top quality There are a lot of crooks everywhere. However, if you order transistors that are manufactured directly in China, it is much more difficult to run into shit. And it is for this reason that I prefer STP and STW transistors, and I don’t even disdain buying from disassembly, i.e. BOO.

POPULAR TRANSISTORS FOR SWITCHED POWER SUPPLY
NAME	VOLTAGE			POWER	CAPACITY SHUTTER	Qg (MANUFACTURER)
NETWORK (220 V)
						17...23nC ( ST)
						38...50nC ( ST)
						35...40nC ( ST)
						39...50nC ( ST)
						46nC ( ST)
						50...70nC ( ST)
						75nC( ST)
						84nC ( ST)
						65nC ( ST)
						46nC ( ST)
						50...70nC ( ST)
						75nC( ST)
						65nC ( ST)
STP20NM60FP						54nC ( ST)
						150nC (IR) 75nC( ST)
						150...200nC (IN)
						252...320nC (IN)
						87...117nC ( ST)

I g \u003d Q g / t on \u003d 63 x 10 -9 / 120 x 10 -9 \u003d 0.525 (A) (1)

With the amplitude of the control voltage pulses at the gate Ug = 15 V, the sum of the output resistance of the driver and the resistance of the limiting resistor should not exceed:

R max = U g / I g = 15 / 0.525 = 29 (ohm) (2)

We calculate the output output impedance of the driver stage for the IR2155 chip:

R on \u003d U cc / I max \u003d 15V / 210mA \u003d 71.43 ohms
R off \u003d U cc / I max \u003d 15V / 420mA \u003d 33.71 ohms

Considering the calculated value according to the formula (2) Rmax = 29 Ohm, we come to the conclusion that with the IR2155 driver it is impossible to obtain the specified speed of the IRF840 transistor. If a resistor Rg = 22 Ohm is installed in the gate circuit, we determine the turn-on time of the transistor as follows:

RE on = R on + R gate, where RE - total resistance, R R gate - resistance installed in the gate circuit of the power transistor = 71.43 + 22 = 93.43 ohms;
I on \u003d U g / RE on, where I on is the opening current, U g - gate control voltage value = 15 / 93.43 = 160mA;
t on \u003d Q g / I on \u003d 63 x 10-9 / 0.16 \u003d 392nS
The turn-off time can be calculated using the same formulas:
RE off = R out + R gate, where RE - total resistance, R out - driver output impedance, R gate - resistance installed in the gate circuit of the power transistor = 36.71 + 22 = 57.71 ohms;
I off \u003d U g / RE off, where I off - opening current, U g - gate control voltage value = 15 / 58 = 259mA;
t off \u003d Q g / I off \u003d 63 x 10-9 / 0.26 \u003d 242nS
To the resulting values, it is necessary to add the time of its own opening - the closing of the transistor, as a result of which real time t on will be 392 + 40 = 432nS, and t off 242 + 80 = 322nS.
Now it remains to make sure that one power transistor has time to completely close before the second one starts to open. To do this, add t on and t off getting 432 + 322 = 754 nS, i.e. 0.754µS. What is it for? The fact is that any of the microcircuits, be it IR2151, or IR2153, or IR2155, has a fixed value DEAD TIME, which is 1.2 µS and does not depend on the frequency of the master oscillator. The datasheet mentions that Deadtime (typ.) is 1.2 µs, but there is also a very embarrassing figure from which the conclusion suggests itself that DEAD TIME is 10% of the duration of the control pulse:

To dispel doubts, the microcircuit was turned on and a two-channel oscilloscope was connected to it:

The power supply was 15 V, and the frequency was 96 kHz. As can be seen from the photograph, with a sweep of 1 µS, the duration of the pause is quite a bit more than one division, which exactly corresponds to approximately 1.2 µS. Next, reduce the frequency and see the following:

As you can see from the photo at 47kHz, the pause time didn't really change, hence the sign saying Deadtime (typ.) 1.2 µs is true.
Since the microcircuit was already working, it was impossible to resist one more experiment - to reduce the supply voltage to make sure that the generator frequency increased. The result is the following picture:

However, the expectations were not justified - instead of increasing the frequency, it decreased, and by less than 2%, which can generally be neglected and it should be noted that the IR2153 chip keeps the frequency quite stable - the supply voltage has changed by more than 30%. It should also be noted that the pause time has slightly increased. This fact is somewhat pleasing - with a decrease in the control voltage, the opening time - closing of the power transistors slightly increases and an increase in the pause in this case will be very useful.
It was also found out that UV DETECT copes with its function perfectly - with a further decrease in the supply voltage, the generator stopped, and with an increase, the microcircuit started up again.
Now let's get back to our math, according to the results of which we found out that with 22 Ohm resistors installed in the gates, the closing and opening times are 0.754 µS for the IRF840 transistor, which is less than the 1.2 µS pause given by the microcircuit itself.
Thus, with the IR2155 microcircuit through 22 Ohm resistors, it will be quite possible to control the IRF840, but the IR2151 will most likely die for a long time, since to close and open the transistors we needed a current of 259 mA and 160 mA, respectively, and its maximum values ​​are 210 mA and 100 ma. Of course, you can increase the resistances installed in the gates of power transistors, but in this case there is a risk of going beyond DEAD TIME. In order not to engage in fortune-telling on coffee grounds, a table was compiled in EXCEL, which you can take. It is assumed that the supply voltage of the microcircuit is 15 V.
To reduce switching noise and to slightly reduce the closing time of power transistors in switching power supplies, either a power transistor is shunted with a resistor and a capacitor connected in series, or the power transformer itself is shunted in the same circuit. This node is called a snubber. The snubber circuit resistor is chosen with a value of 5–10 times the drain resistance - the source of the field-effect transistor in the open state. The capacitance of the circuit capacitor is determined from the expression:
C \u003d tdt / 30 x R
where tdt is the pause time for switching the upper and lower transistors. Based on the fact that the duration of the transient, equal to 3RC, should be 10 times less than the duration of the dead time tdt.
Damping delays the opening and closing moments of the field-effect transistor relative to the control voltage drops at its gate and reduces the rate of voltage change between the drain and the gate. As a result, the peak values ​​of the current pulses are smaller, and their duration is longer. Almost without changing the turn-on time, the damping circuit significantly reduces the turn-off time of the field-effect transistor and limits the spectrum of radio interference generated.

With the theory sorted out a bit, you can proceed to practical schemes.
The simplest IR2153 switching power supply circuit is an electronic transformer with a minimum of functions:

There are no additional functions in the circuit, and the secondary bipolar power supply is formed by two rectifiers with a midpoint and a pair of dual Schottky diodes. The capacitance of the capacitor C3 is determined on the basis of 1 microfarad of capacitance per 1 W of load. Capacitors C7 and C8 are of equal capacity and are located in the range from 1 uF to 2.2 uF. The power depends on the core used and the maximum current of the power transistors and theoretically can reach 1500 watts. However, this is only THEORY , assuming 155 VAC is applied to the transformer and the maximum current of the STP10NK60Z reaches 10A. In practice, in all datasheets, a decrease in the maximum current is indicated depending on the temperature of the transistor crystal, and for the STP10NK60Z transistor, the maximum current is 10 A at a crystal temperature of 25 degrees Celsius. At a crystal temperature of 100 degrees Celsius, the maximum current is already 5.7 A, and we are talking about the temperature of the crystal, and not the heat sink flange, and even more so about the temperature of the radiator.
Therefore, the maximum power should be selected based on the maximum current of the transistor divided by 3 if this is a power supply for a power amplifier and divided by 4 if this is a power supply for a constant load, such as incandescent lamps.
Given the above, we get that for a power amplifier you can get a switching power supply with a power of 10 / 3 \u003d 3.3A, 3.3A x 155V \u003d 511W. For a constant load, we get a power supply 10 / 4 \u003d 2.5 A, 2.5 A x 155V \u003d 387W. In both cases, 100% efficiency is used, which does not happen in nature.. In addition, if we proceed from the fact that 1 μF of the primary power capacitance per 1 W of load power, then we need a capacitor or capacitors with a capacity of 1500 μF, and such a capacitance already needs to be charged through soft start systems.
A switching power supply with overload protection and soft start for secondary power is shown in the following diagram:

First of all, this power supply has overload protection, made on the current transformer. Details on the calculation of the current transformer can be read. However, in the vast majority of cases, a ferrite ring with a diameter of 12 ... 16 mm is quite sufficient, on which about 60 ... 80 turns are wound into two wires. Diameter 0.1...0.15 mm. Then the beginning of one winding is connected to the ends of the second. That's what it is secondary winding. The primary winding contains one or two, sometimes one and a half turns are more convenient.
Also in the circuit, the values ​​​​of the resistor R4 and R6 are reduced in order to expand the range of the primary supply voltage (180 ... 240V). In order not to overload the zener diode installed in the microcircuit, the circuit has a separate zener diode with a power of 1.3 W at 15 V.
In addition, a soft start for secondary power was introduced into the power supply, which made it possible to increase the capacity of the secondary power filters to 1000 μF at an output voltage of ±80 V. Without this system, the power supply went into protection at the moment of switching on. The principle of operation of the protection is based on the operation of the IR2153 at an increased frequency at the time of switching on. This causes losses in the transformer and it is not able to deliver maximum power to the load. As soon as the generation through the divider R8-R9, the voltage supplied to the transformer enters the detector VD5 and VD7 and the charging of the capacitor C7 begins. As soon as the voltage becomes sufficient to open VT1, C3 is connected to the frequency-setting chain of the microcircuit and the microcircuit reaches the operating frequency.
Additional inductances for the primary and secondary voltages have also been introduced. The primary power inductance reduces the interference generated by the power supply and goes to the 220V network, and the secondary one reduces RF ripple at the load.
In this version, there are two additional secondary power supply. The first is designed to power a computer twelve-volt cooler, and the second is to power the preliminary stages of the power amplifier.
Another sub-variant of the circuit is a switching power supply with a unipolar output voltage:

Of course, that the secondary winding counts on the voltage that is needed. The power supply can be soldered on the same board without mounting elements that are not on the diagram.

The next version of the switching power supply is capable of delivering about 1500 W to the load and contains soft start systems for both primary and secondary power, has overload protection and voltage for the forced cooling cooler. The problem of controlling powerful power transistors is solved by using emitter followers on transistors VT1 and VT2, which discharge the gate capacitance of powerful transistors through themselves:

Such forcing the closing of power transistors allows the use of quite powerful instances, such as IRFPS37N50A, SPW35N60C3, not to mention IRFP360 and IRFP460.
At the time of switching on, the voltage at diode bridge primary power is supplied through resistor R1, since the contacts of relay K1 are open. Further, the voltage, through R5, is supplied to the microcircuit and through R11 and R12 to the output of the relay winding. However, the voltage increases gradually - C10 is quite large capacity. From the second winding of the relay, voltage is supplied to the zener diode and thyristor VS2. As soon as the voltage reaches 13 V, it will already be enough to open VS2 after passing the 12 volt zener diode. It should be recalled here that IR2155 starts at a supply voltage of approximately 9 V, therefore, at the time of opening VS2 through IR2155 it will already generate control pulses, only they will enter the primary winding through resistor R17 and capacitor C14, since the second group of contacts of relay K1 is also open . This will significantly limit the charge current of the secondary power filter capacitors. As soon as the thyristor VS2 opens, voltage will be applied to the relay winding and both contact groups shut up. The first shunts the current-limiting resistor R1, and the second shunts R17 and C14.
The power transformer has a service winding and a rectifier based on VD10 and VD11 diodes, from which the relay will be powered, as well as additional feeding of the microcircuit. R14 serves to limit the current of the forced cooling fan.
Used thyristors VS1 and VS2 - MCR100-8 or similar in TO-92 package
Well, at the end of this page, another circuit is all on the same IR2155, but this time it will act as a voltage regulator:

As in the previous version, the power transistors are closed by bipolars VT4 and VT5. The circuit is equipped with a secondary voltage soft start on VT1. Start is made from onboard network car and then the power is supplied by a stabilized voltage of 15 V, fed by diodes VD8, VD9, resistor R10 and zener diode VD6.
In this scheme, there is another rather interesting element - tC. This is a heatsink overheating protection that can be used with almost any inverter. It was not possible to find an unambiguous name, in common people this is a self-resetting thermal fuse, in price lists it usually has the designation KSD301. It is used in many household electrical appliances as a protective or temperature regulating element, since they are produced with different response temperatures. The fuse looks like this:

As soon as the heatsink temperature reaches the cut-out limit of the fuse, the control voltage from the REM point will be removed and the inverter will turn off. After the temperature drops by 5-10 degrees, the fuse will be restored and supply control voltage and the converter will start up again. The same thermal fuse, well, or a thermal relay can also be used in network power supplies by controlling the temperature of the radiator and turning off the power, preferably low-voltage, going to the microcircuit - the thermal relay will work longer this way. You can buy KSD301.
VD4, VD5 - fast diodes from the SF16, HER106 series, etc.
Overload protection can be introduced into the circuit, but during its development, the main emphasis was on miniaturization - even the softstart node was a big question.
Manufacturing of winding parts and printed circuit boards described on the following pages of the article.

Well, in the end, several circuits of switching power supplies found on the Internet.
Scheme No. 6 is taken from the SOLDERING IRON website:

In the next power supply on the self-clocked driver IR2153, the capacity of the booster capacitor is reduced to a minimum sufficiency of 0.22 microfarads (C10). The microcircuit is powered from the artificial midpoint of the power transformer, which is not important. There is no overload protection, the shape of the voltage supplied to the power transformer is slightly corrected by the inductance L1:

Choosing schemes for this article, I came across this one. The idea is to use two IR2153s in a bridge converter. The idea of ​​the author is quite understandable - the output RS of the trigger is fed to the input Ct and, logically, control pulses opposite in phase should be formed at the outputs of the slave microcircuit.
The idea intrigued and an investigative experiment on the topic of working capacity testing was carried out. It was not possible to get stable control pulses at the outputs of IC2 - either the upper driver was working, or the lower one. In addition, the pause phase DEAD TIME, on one chip relative to another, which will significantly reduce the efficiency and the idea was forced to be abandoned.

A distinctive feature of the next power supply on the IR2153 is that if it works, then this work is akin to a powder keg. First of all, an additional winding on the power transformer to power the IR2153 itself caught my eye. However, there is no current-limiting resistor after diodes D3 and D6, which means that the fifteen-volt zener diode inside the microcircuit will be VERY heavily loaded. What happens when it overheats and thermal breakdown can only be guessed at.
Overload protection on VT3 shunts the time-setting capacitor C13, which is quite acceptable.

The last acceptable power supply circuit on the IR2153 is nothing unique. True, the author for some reason too much reduced the resistance of the resistors in the gates of power transistors and installed zener diodes D2 and D3, the purpose of which is not very clear. In addition, the capacitance C11 is too small, although it is possible that we are talking about a resonant converter.

There is another option for a switching power supply using IR2155 and it is for controlling a bridge converter. But there, the microcircuit controls power transistors through an additional driver and a matching transformer, and we are talking about induction melting of metals, so this option deserves a separate page, and everyone who understands at least half of what they read should go to the page with printed circuit boards.

VIDEO INSTRUCTIONS FOR SELF-ASSEMBLY
PULSE POWER SUPPLY BASED ON IR2153 OR IR2155

A few words about the manufacture of pulse transformers:

How to determine the number of turns without knowing the brand of ferrite: